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PDF LT1230 Data sheet ( Hoja de datos )
| Número de pieza | LT1230 | |
| Descripción | Dual and Quad 100MHz Current Feedback Amplifiers | |
| Fabricantes | Linear Technology | |
| Logotipo |  |
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FEATURES
s 100MHz Bandwidth
s 1000V/µs Slew Rate
s Low Cost
s 30mA Output Drive Current
s 0.04% Differential Gain
s 0.1° Differential Phase
s High Input Impedance: 25MΩ, 3pF
s Wide Supply Range: ±2V to ±15V
s Low Supply Current: 6mA Per Amplifier
s Inputs Common Mode to Within 1.5V of Supplies
s Outputs Swing Within 0.8V of Supplies
U
APPLICATIO S
s Video Instrumentation Amplifiers
s Cable Drivers
s RGB Amplifiers
s Test Equipment Amplifiers
LT1229/LT1230
Dual and Quad 100MHz
Current Feedback Amplifiers
DESCRIPTIO
The LT®1229/LT1230 dual and quad 100MHz current
feedback amplifiers are designed for maximum perfor-
mance in small packages. Using industry standard pinouts,
the dual is available in the 8-pin miniDIP and the 8-pin SO
package while the quad is in the 14-pin DIP and 14-pin SO.
The amplifiers are designed to operate on almost any
available supply voltage from 4V (±2V) to 30V (±15V).
These current feedback amplifiers have very high input
impedance and make excellent buffer amplifiers. They
maintain their wide bandwidth for almost all closed-loop
voltage gains. The amplifiers drive over 30mA of output
current and are optimized to drive low impedance loads,
such as cables, with excellent linearity at high frequencies.
The LT1229/LT1230 are manufactured on Linear
Technology’s proprietary complementary bipolar process.
For a single amplifier like these see the LT1227 and for
better DC accuracy see the LT1223.
, LTC and LT are registered trademarks of Linear Technology Corporation.
TYPICAL APPLICATIO
Video Loop Through Amplifier
RG1
3.01k
RF1
750Ω
RG2
187Ω
RF2
750Ω
–
1/2
3.01k VIN– LT1229
+
12.1k
3.01k VIN+
–
1/2
LT1229
+
VOUT
12.1k
1% RESISTORS
WORST CASE CMRR = 22dB
TYPICALLY = 38dB
BNC INPUTS
HIGH INPUT RESISTANCE DOES NOT LOAD CABLE EVEN
WHEN POWER IS OFF
VOUT = G (VIN+ – VIN–)
RF1 = RF2
RG1 = (G – 1) RF2
RG2 =
RF2
G–1
TRIM CMRR WITH RG1
LT1229 • TA01
Loop Through Amplifier Frequency
Response
10
0
NORMAL SIGNAL
–10
–20
–30
–40
COMMON MODE SIGNAL
–50
–60
10 100
1k 10k 100k 1M 10M 100M
FREQUENCY (Hz)
LT1229 • TA02
1
1 page  
LT1229/LT1230
TYPICAL PERFOR A CE CHARACTERISTICS
Voltage Gain and Phase vs
Frequency, Gain = 6dB
8
PHASE
7
6
GAIN
5
4
0
45
90
135
180
3
2
1
0 VS = ±15V
RL = 100Ω
–1 RF = 750Ω
–2
0.1
1
225
10 100
FREQUENCY (MHz)
LT1229 • TPC01
Voltage Gain and Phase vs
Frequency, Gain = 20dB
22
PHASE
21
20
GAIN
19
18
0
45
90
135
180
17
16
15
14 VS = ±15V
RL = 100Ω
13 RF = 750Ω
12
0.1
1
225
10 100
FREQUENCY (MHz)
LT1229 • TPC04
Voltage Gain and Phase vs
Frequency, Gain = 40dB
42
PHASE
41
40
GAIN
39
38
0
45
90
135
180
37
36
35
34 VS = ±15V
33
RL = 100Ω
RF = 750Ω
32
0.1
1
225
10 100
FREQUENCY (MHz)
LT1229 • TPC07
– 3dB Bandwidth vs Supply
Voltage, Gain = 2, RL = 100Ω
180
160
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
140
120 RF = 500Ω
100 RF = 750Ω
80 RF = 1k
60
40
RF = 2k
20
0
0 2 4 6 8 10 12 14 16 18
SUPPLY VOLTAGE (±V)
LT1229 • TPC02
– 3dB Bandwidth vs Supply
Voltage, Gain = 2, RL = 1k
180
160
140 RF = 500Ω
120
RF = 750Ω
100
80
60
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
40 RF = 1k
20
RF = 2k
0
0 2 4 6 8 10 12 14 16 18
SUPPLY VOLTAGE (±V)
LT1229 • TPC03
– 3dB Bandwidth vs Supply
Voltage, Gain = 10, RL = 100Ω
180
160
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
140
120
100 RF = 250Ω
80 RF = 500Ω
RF = 750Ω
60
40 RF = 1k
20 RF = 2k
0
0 2 4 6 8 10 12 14 16 18
SUPPLY VOLTAGE (±V)
LT1229 • TPC05
– 3dB Bandwidth vs Supply
Voltage, Gain = 10, RL = 1k
180
160
PEAKING ≤ 0.5dB
PEAKING ≤ 5dB
140
120
RF = 250Ω
RF = 500Ω
100
80 RF = 750Ω
60 RF = 1k
40
20 RF = 2k
0
0 2 4 6 8 10 12 14 16 18
SUPPLY VOLTAGE (±V)
LT1229 • TPC06
– 3dB Bandwidth vs Supply
Voltage, Gain = 100, RL = 100Ω
18
16
14
12
RF = 500Ω
10
RF = 1k
8
6 RF = 2k
4
2
0
0 2 4 6 8 10 12 14 16 18
SUPPLY VOLTAGE (±V)
LT1229 • TPC08
– 3dB Bandwidth vs Supply
Voltage, Gain = 100, RL = 1kΩ
18
16
14 RF = 500Ω
12
10 RF = 1k
8
RF = 2k
6
4
2
0
0 2 4 6 8 10 12 14 16 18
SUPPLY VOLTAGE (±V)
LT1229 • TPC09
5
5 Page 
LT1229/LT1230
APPLICATI S I FOR ATIO
Crosstalk and Cascaded Amplifiers
The amplifiers in the LT1229/LT1230 do not share any
common circuitry. The only thing the amplifiers share is
the supplies. As a result, the crosstalk between amplifiers
is very low. In a good breadboard or with a good PC board
layout the crosstalk from the output of one amplifier to the
input of another will be over 100dB down, up to 100kHz
and 65dB down at 10MHz. The following curve shows
the crosstalk from the output of one amplifier to the
input of another.
Amplifier Crosstalk vs Frequency
120
VS = ±15V
110 AV = 10
RS = 50Ω
100 RL = 100Ω
90
80
70
60
50
10 100
1k 10k 100k 1M 10M 100M
FREQUENCY (Hz)
LT1229 • TA12
The high frequency crosstalk between amplifiers is
caused by magnetic coupling between the internal wire
bonds that connect the IC chip to the package lead frame.
The amount of crosstalk is inversely proportional to the
load resistor the amplifier is driving, with no load (just
the feedback resistor) the crosstalk improves 18dB. The
curve shows the crosstalk of the LT1229 amplifier B
output (Pin 7) to the input of amplifier A. The crosstalk
from amplifier A’s output (Pin 1) to amplifier B is about
10dB better. The crosstalk between all of the LT1230
amplifiers is as shown. The LT1230 amplifiers that are
separated by the supplies are a few dB better.
When cascading amplifiers the crosstalk will limit the
amount of high frequency gain that is available because
the crosstalk signal is out of phase with the input signal.
This will often show up as unusual frequency response.
For example: cascading the two amplifiers in the LT1229,
each set up with 20dB of gain and a –3dB bandwidth of
65MHz into 100Ω will result in 40dB of gain, BUT the
response will start to drop at about 10MHz and then flatten
out from 20MHz to 30MHz at about 0.5dB down. This is
due to the crosstalk back to the input of the first amplifier.
For best results when cascading amplifiers use the LT1229
and drive amplifier B and follow it with amplifier A.
TYPICAL APPLICATI S
Single 5V Supply Cable Driver for Composite Video
This circuit amplifies standard 1V peak composite video
input (1.4VP-P) by two and drives an AC coupled, doubly
terminated cable. In order for the output to swing
2.8VP-P on a single 5V supply, it must be biased accu-
rately. The average DC level of the composite input is a
function of the luminance signal. This will cause problems
if we AC couple the input signal into the amplifier because
a rapid change in luminance will drive the output into the
rails. To prevent this we must establish the DC level at the
input and operate the amplifier with DC gain.
The transistor’s base is biased by R1 and R2 at 2V. The
emitter of the transistor clamps the noninverting input of
the amplifier to 1.4V at the most negative part of the input
(the sync pulses). R4, R5 and R6 set the amplifier up with
a gain of two and bias the output so the bottom of the sync
pulses are at 1.1V. The maximum input then drives the
output to 3.9V.
5V
2N3904
C1
1µF
R1
3k
R2
2k
VIN
R3
150k
C2
1µF
R5
750Ω
R4
1.5k
+
1/2
LT1229
–
C3
47µF
C4 VOUT
1000µF R7
75Ω
R6
510Ω
R8
10k
LT1229 • TA11
11
11 Page | ||
| Páginas | Total 16 Páginas | |
| PDF Descargar | [ Datasheet LT1230.PDF ] | |
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