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PDF LT1996 Data sheet ( Hoja de datos )
| Número de pieza | LT1996 | |
| Descripción | 100uA Gain Selectable Amplifier | |
| Fabricantes | Linear Technology | |
| Logotipo |  |
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FEATURES
■ Pin Configurable as a Difference Amplifier,
Inverting and Noninverting Amplifier
■ Difference Amplifier
Gain Range 9 to 117
CMRR >80dB
■ Noninverting Amplifier
Gain Range 0.008 to 118
■ Inverting Amplifier
Gain Range –0.08 to –117
■ Gain Error: <0.05%
■ Gain Drift: < 3ppm/°C
■ Wide Supply Range: Single 2.7V to Split ±18V
■ Micropower Operation: 100µA Supply
■ Input Offset Voltage: 50µV (Max)
■ Gain Bandwidth Product: 560kHz
■ Rail-to-Rail Output
■ Space Saving 10-Lead MSOP and DFN Packages
U
APPLICATIO S
■ Handheld Instrumentation
■ Medical Instrumentation
■ Strain Gauge Amplifiers
■ Differential to Single-Ended Conversion
, LTC and LT are registered trademarks of Linear Technology Corporation.
All other trademarks are the property of their respective owners. Patents Pending.
LT1996
Precision, 100µA
Gain Selectable Amplifier
DESCRIPTIO
The LT®1996 combines a precision operational amplifier
with eight precision resistors to form a one-chip solution
for accurately amplifying voltages. Gains from –117 to
118 with a gain accuracy of 0.05% can be achieved without
any external components. The device is particularly well
suited for use as a difference amplifier, where the excellent
resistor matching results in a common mode rejection
ratio of greater than 80dB.
The amplifier features a 50µV maximum input offset
voltage and a gain bandwidth product of 560kHz. The
device operates from any supply voltage from 2.7V to 36V
and draws only 100µA supply current on a 5V supply. The
output swings to within 40mV of either supply rail.
The internal resistors have excellent matching character-
istics; variation is 0.05% over temperature with a guaran-
teed matching temperature coefficent of less than 3ppm/°C.
The resistors are also extremely stable over voltage,
exhibiting a nonlinearity of less than 10ppm.
The LT1996 is fully specified at 5V and ±15V supplies and
from –40°C to 85°C. The device is available in space
saving 10-lead MSOP and DFN packages. For an amplifier
with selectable gains from –13 to 14, see the LT1991 data
sheet.
TYPICAL APPLICATIO
VM(IN) –
∆VIN
+
VP(IN)
INPUT RANGE
±60V
RIN = 100kΩ
Rail-to-Rail Gain = 9 Difference Amplifier
15V
450k/81
450k/27
450k/9
450k/9
450k/27
450k/81
450k
4pF
–
+
4pF
LT1996
450k
VOUT = VREF + 9 • ∆VIN
SWING 40mV TO
EITHER RAIL
–15V
VREF
1996 TA01
DataSheet4 U .com
Distribution of Resistor Matching
40 LT1996A
35 G = 81
30
25
20
15
10
5
0
– 0.04
– 0.02
0
0.02
RESISTOR MATCHING (%)
0.04
1996 TA01b
1996f
1
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LT1996
ELECTRICAL CHARACTERISTICS
Note 4: Both the LT1996C and LT1996I are guaranteed functional over the
–40°C to 85°C temperature range.
Note 5: The LT1996C is guaranteed to meet the specified performance
from 0°C to 70°C and is designed, characterized and expected to meet
specified performance from –40°C to 85°C but is not tested or QA
sampled at these temperatures. The LT1996I is guaranteed to meet
specified performance from –40°C to 85°C.
Note 6: This parameter is not 100% tested.
Note 7: Input voltage range is guaranteed by the CMRR test at VS = ±15V.
For the other voltages, this parameter is guaranteed by design and through
correlation with the ±15V test. See the Applications Information section to
determine the valid input voltage range under various operating
conditions.
Note 8: Offset voltage, offset voltage drift and PSRR are defined as
referred to the internal op amp. You can calculate output offset as follows.
In the case of balanced source resistance, VOS, OUT = VOS • Noise Gain +
IOS • 450k + IB • 450k • (1 – RP/RN) where RP and RN are the total
resistance at the op amp positive and negative terminal respectively.
Note 9: Resistors connected to the minus inputs. Resistor matching is not
tested directly, but is guaranteed by the gain error test.
Note 10: Input impedance is tested by a combination of direct
measurements and correlation to the CMRR and gain error tests.
TYPICAL PERFOR A CE CHARACTERISTICS (Difference Amplifier Configuration)
Supply Current vs Supply Voltage
200
175
150 TA = 25°C
125
100
TA = 85°C
TA = –40°C
75
50
25
0
0 2 4 6 8 10 12 14 16 18 20
SUPPLY VOLTAGE (±V)
1996 G01
Output Voltage Swing vs Load
Current (Output High)
VCC
–100
VS = 5V, 0V
–200
–300
–400
–500
TA = 85°C
TA = 25°C
TA = –40°C
–600
–700
–800
–900
–1000
0 1 2 3 4 5 6 7 8 9 10
LOAD CURRENT (mA)
1996 G04
Output Voltage Swing vs
Temperature
VS = 5V, 0V
NO LOAD
OUTPUT HIGH
(RIGHT AXIS)
VCC
–20
–40
–60
60
40
OUTPUT LOW
20 (LEFT AXIS)
VEE
–50 –25
0 25 50 75
TEMPERATURE (°C)
100 125
1996 G02
Output Short-Circuit Current vs
Temperature
25
VS = 5V, 0V
20
SINKING
15
10 SOURCING
5
0
–50 –25
0 25 50 75 100 125
TEMPERATURE (°C)
1996 G05
Output Voltage Swing vs Load
Current (Output Low)
1400 VS = 5V, 0V
1200
1000
TA = 85°C
800
TA = 25°C
600
400
TA = –40°C
200
VEE
0 1 2 3 4 5 6 7 8 9 10
LOAD CURRENT (mA)
1996 G03
Input Offset Voltage vs
Difference Gain
150
VS = 5V, 0V
REPRESENTATIVE PARTS
100
50
0
–50
–100
–150
9 18 27 36 45 54 63 72 81 90 99 108 117
GAIN (V/V)
1996 G06
DataSheet4 U .com
1996f
5
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LT1996
APPLICATIO S I FOR ATIO
suggested in Figure 1: raise VREF, lower VEE, or provide
some negative VMORE.
Likewise, from the lower common mode extreme, making
the negative input more negative will raise the output
voltage, limited by VCC – 0.04V.
MIN VMORE = (VREF – VCC + 0.04V) • RG/RF
(should be negative)
Again, the additional input range calculated here is only
available provided the other remaining constraint is not
violated, the maximum voltage allowed on the pin.
The Classical Noninverting Amplifier: High Input Z
Perhaps the most common op amp configuration is the
noninverting amplifier. Figure 4 shows the textbook
RF
RG
–
VIN +
VOUT
VOUT = GAIN • VIN
GAIN = 1 + RF/RG
CLASSICAL NONINVERTING OP AMP CONFIGURATION.
YOU PROVIDE THE RESISTORS.
8 450k/81
9 450k/27
10 450k/9
1 450k/9
2 450k/27
450k
4pF
–
+
4pF
6
VOUT
3 450k/81
450k
LT1996
5
VIN
CLASSICAL NONINVERTING OP AMP CONFIGURATION
IMPLEMENTED WITH LT1991. RF = 45k, RG = 5.6k, GAIN = 9.1.
GAIN IS ACHIEVED BY GROUNDING, FLOATING OR FEEDING BACK
THE AVAILABLE RESISTORS TO ARRIVE AT DESIRED RF AND RG.
WE PROVIDE YOU WITH <0.1% RESISTORS.
1996 F04
Figure 4. The LT1996 as a Classical Noninverting Op Amp
DataSheet4 U .com
representation of the circuit on the top. The LT1996 is
shown on the bottom configured in a precision gain of 9.1.
One of the benefits of the noninverting op amp configura-
tion is that the input impedance is extremely high. The
LT1996 maintains this benefit. Given the finite number of
available feedback resistors in the LT1996, the number of
gain configurations is also finite. The complete list of such
Hi-Z input noninverting gain configurations is shown in
Table 1. Many of these are also represented in Figure 5 in
schematic form. Note that the P-side resistor inputs have
been connected so as to match the source impedance
seen by the internal op amp inputs. Note also that gain and
noise gain are identical, for optimal precision.
Table 1. Configuring the M Pins for Simple Noninverting Gains.
The P Inputs are driven as shown in the examples on the next
page
M81, M27, M9 Connection
Gain M81 M27
M9
1
Output
Output
Output
1.08
Output
Output
Grounded
1.11 Output Float Grounded
1.30
Output
Grounded
Output
1.32
Float
Output
Grounded
1.33
Output
Grounded
Float
1.44
Output
Grounded
Grounded
3.19
Grounded
Output
Output
3.7
Float Grounded
Output
3.89
Grounded
Output
Float
4.21
Grounded
Output
Grounded
9.1
Grounded
Float
Output
10 Float Float Grounded
11.8
Grounded
Grounded
Output
28
Float Grounded
Float
37
Float
Grounded
Grounded
82
Grounded
Float
Float
91
Grounded
Float
Grounded
109
Grounded
Grounded
Float
118
Grounded
Grounded
Grounded
1996f
11
11 Page | ||
| Páginas | Total 24 Páginas | |
| PDF Descargar | [ Datasheet LT1996.PDF ] | |
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